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1 for more information www.linear.com/ltc7138 typical a pplica t ion fea t ures descrip t ion high efficiency, 140v 400ma step-down regulator the lt c ? 7138 is a high efficiency step-down dc/dc regulator with internal power switch that draws only 12a typical dc supply current while maintaining a regulated output voltage at no load. the ltc7138 can supply up to 400ma load current and features a programmable peak current limit that provides a simple method for optimizing efficiency and for reduc - ing output ripple and component size. the ltc7138s combination of burst mode ? operation, integrated power switch, low quiescent current, and programmable peak current limit provides high efficiency over a broad range of load currents. with its wide input range of 4v to 140v and programmable overvoltage lockout, the ltc7138 is a robust regulator suited for regulating from a wide variety of power sources. additionally, the ltc7138 includes a precise run threshold and soft-start feature to guarantee that the power system start-up is well-controlled in any environment. a feedback comparator output enables multiple ltc7138s to be con - nected in parallel for higher current applications. the l tc7138 is available in a thermally enhanced high voltage-capable 16-lead mse package with four missing pins. l , lt, ltc, ltm, burst mode, linear technology and the linear logo are registered trademarks of linear technology corporation. all other trademarks are the property of their respective owners. efficiency and power loss vs load current 5v to 140v input to 5v output, 400ma step-down regulator a pplica t ions n wide operating input voltage range: 4v to 140v n internal low resistance power mosfet n no compensation required n adjustable 100ma to 400ma maximum output current n low dropout operation: 100% duty cycle n low quiescent current: 12a n wide output range: 0.8v to v in n 0.8v 1% feedback voltage reference n precise run pin threshold n internal or external soft-start n programmable 1.8v, 3.3v , 5v or adjustable output n few external components required n programmable input overvoltage lockout n thermally enhanced high voltage msop package n industrial control supplies n medical devices n distributed power systems n portable instruments n battery-operated devices n avionics n automotive 7138 ta01a anode v fb sw l1 220h v in run c in 1f 250v c out 22f v in 5v to 140v v out 5v 400ma ltc7138 gnd v prg2 ovlo ss v prg1 v in = 12v v in = 48v v in = 140v load current (ma) 30 efficiency (%) power loss (mw) 90 100 20 10 80 50 70 10 1 100 1000 60 40 0.1 100 1000 7138 ta01b 0 10 1 efficiency power loss ltc7138 7138f
2 for more information www.linear.com/ltc7138 a bsolu t e maxi m u m r a t ings 1 3 5 6 7 8 sw v in fbo v prg2 v prg1 gnd 16 14 12 11 10 9 anode run ovlo i set ss v fb top view 17 gnd mse package variation: mse16 (12) 16-lead plastic msop t jmax = 150c, ja = 40c/w, jc = 10c/w exposed pad (pin 17) is gnd, must be soldered to pcb p in c on f igura t ion o r d er i n f or m a t ion lead free finish tape and reel part marking* package description temperature range ltc7138emse#pbf ltc7138emse#trpbf 7138 16-lead plastic msop C40c to 125c ltc7138imse#pbf ltc7138imse#trpbf 7138 16-lead plastic msop C40c to 125c ltc7138hmse#pbf ltc7138hmse#trpbf 7138 16-lead plastic msop C40c to 150c ltc7138mpmse#pbf ltc7138mpmse#trpbf 7138 16-lead plastic msop C55c to 150c consult ltc marketing for parts specified with wider operating temperature ranges. *the temperature grade is identified by a label on the shipping container. consult ltc marketing for information on non-standard lead based finish parts. for more information on lead free part marking, go to: http://www.linear.com/leadfree/ for more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ v in supply voltage ................................... C 0.3v to 140v run voltage ............................................. C0.3v to 140v ss, fbo, ovlo, i set voltages ...................... C 0.3v to 6v v fb , v prg1 , v prg2 voltages ......................... C 0.3v to 6v operating junction temperature range (notes 2, 3, 4) ltc7138e, ltc7138i .......................... C4 0c to 125c ltc7138h .......................................... C4 0c to 150c ltc7138mp ....................................... C5 5c to 150c storage temperature range .................. C 65c to 150c lead temperature (soldering, 10 sec) ................... 3 00c (note 1) e lec t rical c harac t eris t ics the l denotes the specifications which apply over the specified operating junction temperature range, otherwise specifications are at t a = 25c (note 2). v in = 12v, unless otherwise noted. symbol parameter conditions min typ max units input supply (v in ) v in input voltage operating range 4 140 v v out output voltage operating range 0.8 v in v uvlo v in undervoltage lockout v in rising v in falling hysteresis l l 3.5 3.3 3.75 3.5 250 4.0 3.8 v v mv i q dc supply current (note 5) active mode sleep mode shutdown mode no load v run = 0v 200 12 1.4 400 22 6 a a a v run run pin threshold run rising run falling hysteresis 1.17 1.06 1.21 1.10 110 1.25 1.14 v v mv i run run pin leakage current run = 1.3v C10 0 10 na v ovlo ovlo pin threshold ovlo rising ovlo falling hysteresis 1.17 1.06 1.21 1.10 110 1.25 1.14 v v mv ltc7138 7138f
3 for more information www.linear.com/ltc7138 e lec t rical c harac t eris t ics the l denotes the specifications which apply over the specified operating junction temperature range, otherwise specifications are at t a = 25c (note 2). v in = 12v, unless otherwise noted. symbol parameter conditions min typ max units output supply (v fb ) v fb(adj) feedback comparator threshold (adjustable output) v fb rising, v prg1 = v prg2 = 0v ltc7138e, ltc7138i ltc7138h, ltc7138mp l l 0.792 0.788 0.800 0.800 0.808 0.812 v v v fbh feedback comparator hysteresis (adjustable output) v fb falling, v prg1 = v prg2 = 0v l 3 5 9 mv i fb feedback pin current v fb = 1v, v prg1 = v prg2 = 0v C10 0 10 na v fb(fixed) feedback comparator thresholds (fixed output) v fb rising, v prg1 = ss, v prg2 = 0v v fb falling, v prg1 = ss, v prg2 = 0v l l 4.94 4.91 5.015 4.985 5.09 5.06 v v v fb rising, v prg1 = 0v, v prg2 = ss v fb falling, v prg1 = 0v, v prg2 = ss l l 3.25 3.23 3.31 3.29 3.37 3.35 v v v fb rising, v prg1 = v prg2 = ss v fb falling, v prg1 = v prg2 = ss l l 1.78 1.77 1.81 1.80 1.84 1.83 v v operation i peak peak current comparator threshold i set floating 100k resistor from i set to gnd i set shorted to gnd l l l 540 270 140 610 310 170 680 350 200 ma ma ma i val valley current comparator threshold relative to i peak i set floating 100k resistor from i set to gnd i set shorted to gnd l l l 50 45 45 60 60 60 70 70 75 % % % r on power switch on-resistance i sw = C100ma 1.8 i lsw switch pin leakage current v in = 140v, sw = 0v 0.1 1 a i ss soft-start pin pull-up current v ss < 2.5v 4 5 6 a t int(ss) internal soft-start time ss pin floating 1 ms note 1: stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. exposure to any absolute maximum rating condition for extended periods may affect device reliability and lifetime. note 2: the ltc7138 is tested under pulsed load conditions such that t j t a . the ltc7138e is guaranteed to meet performance specifications from 0c to 85c. specifications over the C40c to 125c operating junction temperature range are assured by design, characterization and correlation with statistical process controls. the ltc7138i is guaranteed over the C40c to 125c operating junction temperature range, the ltc7138h is guaranteed over the C40c to 150c operating junction temperature range and the ltc7138mp is tested and guaranteed over the C55c to 150c operating junction temperature range. high junction temperatures degrade operating lifetimes; operating lifetime is derated for junction temperatures greater than 125c. note that the maximum ambient temperature consistent with these specifications is determined by specific operating conditions in conjunction with board layout, the rated package thermal impedance and other environmental factors. note 3: the junction temperature (t j , in c) is calculated from the ambient temperature (t a , in c) and power dissipation (p d , in watts) according to the formula: t j = t a + (p d ? ja ) where ja is 40c/w for the msop package. note that the maximum ambient temperature consistent with these specifications is determined by specific operating conditions in conjunction with board layout, the rated package thermal impedance and other environmental factors. note 4: this ic includes overtemperature protection that is intended to protect the device during momentary overload conditions. the maximum rated junction temperature will be exceeded when this protection is active. continuous operation above the specified absolute maximum operating junction temperature may impair device reliability or permanently damage the device. the overtemperature protection level is not production tested. note 5: dynamic supply current is higher due to the gate charge being delivered at the switching frequency. see applications information. ltc7138 7138f
4 for more information www.linear.com/ltc7138 typical p er f or m ance c harac t eris t ics peak current and valley current trip thresholds vs r iset efficiency vs load current, v out = 5v peak current and valley current trip thresholds vs temperature and i set efficiency vs load current, v out = 3.3v peak current and valley current trip thresholds vs input voltage efficiency vs load current, v out = 1.8v efficiency vs input voltage, v out = 5v feedback comparator trip threshold vs temperature run and ovlo thresholds vs temperature 0.1 100 1000 10 1 load current (ma) 30 efficiency (%) 90 100 20 10 80 50 70 60 40 7138 g01 0 figure 13 circuit v in = 12v v in = 48v v in = 140v 30 90 100 20 10 80 50 70 60 40 0 0 25 75 100 50 125 150 input voltage (v) efficiency (%) 7138 g04 i load = 1ma i load = 30ma i load = 400ma figure 13 circuit temperature (c) ?55 798 threshold voltage (mv) 799 800 801 802 ?25 5 35 65 7138 g05 95 125 155 temperature (c) ?55 run or ovlo threshold voltage (v) 1.20 1.22 1.24 35 95 7138 g06 1.18 1.16 1.14 1.12 1.10 ?25 5 65 125 155 1.08 1.06 rising falling 0.1 100 1000 10 1 figure 13 circuit v in = 12v v in = 48v v in = 140v load current (ma) 30 efficiency (%) 90 100 20 10 80 50 70 60 40 7138 g02 0 0.1 100 1000 10 1 figure 13 circuit v in = 12v v in = 48v v in = 140v load current (ma) 30 efficiency (%) 90 100 20 10 80 50 70 60 40 7138 g03 0 voltage (v) 0 30 60 90 120 150 0 100 200 300 400 500 600 700 threshold (ma) 7138 g09 peak current i set open valley current i 175 set 200 open 225 peak current i 0 set 100 gnd 200 valley current i 300 set 400 gnd 500 600 700 threshold (ma) 7138 g07 peak current valley current temperature (c) ?55 ?25 5 35 65 95 125 155 0 100 200 300 400 500 600 700 threshold (ma) ltc7138 7138 g08 7138f peak current i set open r iset (k) valley current i set open 0 peak current i set gnd 25 valley current i set gnd v 50 in 75 100 125 150
5 for more information www.linear.com/ltc7138 typical p er f or m ance c harac t eris t ics switch on-resistance vs input voltage switch on-resistance vs temperature load step transient response quiescent supply current vs input voltage operating waveforms, v in = 48v quiescent supply current vs temperature operating waveforms, v in = 140v switch pin current vs temperature short-circuit and recovery v in voltage (v) 0 0 v in supply current (a) 15 60 90 7138 g10 10 5 30 120 150 sleep shutdown v in voltage (v) 1.0 switch on-resistance () 2.0 1.5 2.5 3.0 7138 g13 0 60 90 30 120 150 temperature (c) ?55 switch on-resistance () 35 7138 g14 2 ?25 5 65 0 1 4 3 95 125 155 i sw = 250ma temperature (c) ?55 ?25 0 v in supply current (a) 10 35 30 25 5 65 95 7138 g11 5 20 15 35 125 155 v in = 140v sleep shutdown temperature (c) ?55 switch pin current (a) 35 7138 g12 ?5 ?25 5 65 ?15 15 10 5 0 ?10 95 125 155 v in = 140v sleep mode sw = 0.8v current into sw sw = 0v current out of sw output voltage 100mv/div load current 200ma/div 200s/div v in = 48v v out = 3.3v 10ma to 400ma load step figure 14 circuit 7138 g15 output voltage 100mv/div switch voltage 20v/div inductor current 500ma/div 10s/div v in = 48v v out = 3.3v i out = 300ma figure 14 circuit 7138 g16 output voltage 100mv/div switch voltage 50v/div inductor current 500ma/div 10s/div v in = 140v v out = 3.3v i out = 300ma figure 14 circuit 7138 g17 output voltage 1v/div inductor current 500ma/div 500s/div figure 14 circuit 7138 g18 ltc7138 7138f
6 for more information www.linear.com/ltc7138 p in func t ions sw (pin 1): switch node connection to inductor and catch diode cathode. this pin connects to the drain of the internal power mosfet switch. v in (pin 3): main supply pin. a ceramic bypass capacitor should be tied between this pin and gnd. fbo (pin 5): feedback comparator output. connect to the v fb pins of additional ltc7138s to combine the output current. the typical pull-up current is 20a. the typical pull- down impedance is 70. see applications information. v prg2 , v prg1 (pins 6, 7): output voltage selection. short both pins to ground for a resistive divider programmable output voltage. short v prg1 to ss and short v prg2 to ground for a 5v output voltage. short v prg1 to ground and short v prg2 to ss for a 3.3v output voltage. short both pins to ss for a 1.8v output voltage. gnd (pin 8, exposed pad pin 17): ground. the exposed pad must be soldered to the pcb ground plane for rated electrical and thermal performance. v fb (pin 9): output voltage feedback. when configured for an adjustable output voltage, connect to an external resistive divider to divide the output voltage down for comparison to the 0.8v reference. for the fixed output configuration, directly connect this pin to the output. ss (pin 10): soft-start control input. a capacitor to ground at this pin sets the output voltage ramp time. a 50a current initially charges the soft-start capacitor until switching begins, at which time the current is reduced to its nominal value of 5a. the output voltage ramp time from zero to its regulated value is 1ms for every 6.25nf of capacitance from ss to gnd. if left floating, the ramp time defaults to an internal 1ms soft-start. i set (pin 11): peak current set input. a resistor from this pin to ground sets the peak current comparator threshold. leave floating for the maximum peak current (610ma typi - cal) or short to ground for minimum peak current (170ma typical). the valley current is typically 60% of the peak current set by this pin. the maximum output current is 75% of the peak current. the 5a current that is sourced out of this pin when switching is reduced to 1a in sleep. optionally, a capacitor can be placed from this pin to gnd to trade off efficiency for light load output voltage ripple. see applications information. ovlo (pin 12): overvoltage lockout input. connect to the input supply through a resistor divider to set the over - voltage lockout level. a voltage on this pin above 1.21v disables the internal mosfet switch. normal operation resumes when the voltage on this pin decreases below 1.10v . exceeding the ovlo lockout threshold triggers a soft-start reset, resulting in a graceful recovery from an input supply transient. this pin must be grounded if the ovlo is not used. run (pin 14): run control input. a voltage on this pin above 1.21v enables normal operation. forcing this pin below 0.7v shuts down the ltc7138, reducing quiescent current to approximately 1.4a. optionally, connect to the input supply through a resistor divider to set the undervoltage lockout. anode (pin 16): catch diode anode sense. this pin is the anode connection for the catch diode. an internal sense resistor is connected between this pin and the exposed pad ground. ltc7138 7138f
7 for more information www.linear.com/ltc7138 b lock diagra m c out c in v in v out + ? + ? + ? + 3 d1 ? + ? + + peak current comparator valley current comparator feedback comparator voltage reference v prg2 gnd gnd ss ss v prg1 gnd ss gnd ss r1 1.0m 4.2m 2.5m 1.0m r2 800k 800k 800k v out adjustable 5v fixed 3.3v fixed 1.8v fixed start-up: 50a normal: 5a implement divider externally for adjustable version v in 1 sw l1 anode i set logic 16 ss r2 r1 5v 5v 20a fbo 70 10 5 gnd 8 gnd 17 v fb 9 v prg1 7 v prg2 7138 bd 6 0.800v ovlo 1.21v 12 1.21v run 14 i set 11 active: 5a sleep: 1a 1.3v + ltc7138 7138f
8 for more information www.linear.com/ltc7138 o pera t ion the ltc7138 is a step-down dc/dc regulator with internal power switch that uses burst mode control, combining low quiescent current with high switching frequency, which results in high efficiency across a wide range of load currents. burst mode operation functions by us - ing short burst cycles to switch the inductor current through the internal power mosfet, followed by a sleep cycle where the power switch is off and the load current is supplied by the output capacitor. during the sleep cycle, the ltc7138 draws only 12a of supply current. at light loads, the burst cycles are a small percentage of the total cycle time which minimizes the average supply current, greatly improving efficiency. figure 1 shows an example of burst mode operation. the switching frequency is de - pendent on the inductor value, peak current, input voltage and output voltage. external feedback resistors (adjustable mode) can be used by connecting both v prg1 and v prg2 to ground. in adjustable mode the feedback comparator monitors the voltage on the v fb pin and compares it to an internal 800mv reference. if this voltage is greater than the refer - ence, the comparator activates a sleep mode in which the power switch and current comparators are disabled, reducing the v in pin supply current to only 12a. as the load current discharges the output capacitor, the voltage on the v fb pin decreases. when this voltage falls 5mv below the 800mv reference, the feedback comparator trips and enables burst cycles. at the beginning of the burst cycle, the internal high side power switch (p-channel mosfet) is turned on and the inductor current begins to ramp up. the inductor current increases until either the current exceeds the peak cur - rent comparator threshold or the voltage on the v fb pin exceeds 800mv, at which time the switch is turned off and the inductor current is carried by the external catch diode. the inductor current, then sensed through the anode pin, ramps down until the current falls below the valley current comparator threshold. if the voltage on the v fb pin is still less than the 800mv reference, the power switch is turned on again and another cycle commences. the average current during a burst cycle will normally be greater than the average load current. for this architecture, the maximum average output current is equal to 75% of the peak current. the hysteretic nature of this control architecture results in a switching frequency that is a function of the input voltage, output voltage, and inductor value. this behavior provides inherent short-circuit protection. if the output is shorted to ground, the inductor current will decay very slowly during a single switching cycle. since the high side switch turns on only when the inductor current is below the valley current trip threshold, the ltc7138 inherently switches at a lower frequency during start-up or short- circuit conditions. burst frequency inductor current output voltage ?v out 7138 f01 burst cycle sleep cycle switching frequency figure 1. burst mode operation main control loop the ltc7138 uses the v prg1 and v prg2 control pins to connect internal feedback resistors to the v fb pin. this enables fixed outputs of 1.8v, 3.3v or 5v without increas - ing component count, input supply current or exposure to noise on the sensitive input to the feedback comparator . (refer to block diagram) ltc7138 7138f
9 for more information www.linear.com/ltc7138 start-up and shutdown if the voltage on the run pin is less than 0.7v, the ltc7138 enters a shutdown mode in which all internal circuitry is disabled, reducing the dc supply current to 1.4a. when the voltage on the run pin exceeds 1.21v, normal operation of the main control loop is enabled. the run pin comparator has 110mv of internal hysteresis, and therefore must fall below 1.1v to disable the main control loop. an internal 1ms soft-start function limits the ramp rate of the output voltage on start-up to prevent excessive input supply droop. if a longer ramp time and consequently less supply droop is desired, a capacitor can be placed from the ss pin to ground. the 5a current that is sourced out of this pin will create a smooth voltage ramp on the capacitor. if this ramp rate is slower than the internal 1ms soft-start, then the output voltage will be limited by the ramp rate on the ss pin. the internal and external soft-start functions are reset on start-up, after an undervoltage or overvoltage event on the input supply, and after an overtemperature shutdown. peak inductor current programming the peak current comparator nominally limits the peak inductor current to 610ma. this peak inductor current can be adjusted by placing a resistor from the i set pin to ground. the 5a current sourced out of this pin through the resistor generates a voltage that adjusts the peak cur - rent comparator threshold. the valley current threshold tracks the peak current threshold setting, and is typically 60% of the peak current. during sleep mode, the current sourced out of the i set pin is reduced to 1a. the i set current is increased back to 5a on the first switching cycle after exiting sleep mode. the i set current reduction in sleep mode, along with adding a filtering network, r iset and c iset , from the i set pin to ground, provides a method of reducing light load output voltage ripple at the expense of lower efficiency and slightly degraded load step transient response. for applications requiring higher output current, the ltc7138 provides a feedback comparator output pin (fbo) for combining the output current of multiple ltc7138s. o pera t ion by connecting the fbo pin of a master ltc7138 to the v fb pin of one or more slave ltc7138s, the output currents can be combined to source 400ma times the number of ltc7138s. dropout operation when the input supply decreases toward the output sup - ply, the duty cycle increases to maintain regulation. the p-channel mosfet switch in the l tc7138 allows the duty cycle to increase all the way to 100%. at 100% duty cycle, the p-channel mosfet stays on continuously, providing output current equal to the peak current, which is greater than the maximum load current when not in dropout. input voltage and overtemperature protection when using the ltc7138, care must be taken not to exceed any of the ratings specified in the absolute maximum rat - ings section. as an added safeguard, however, the ltc7138 incorporates an overtemperature shutdown feature. if the junction temperature reaches approximately 180c, the ltc7138 will enter thermal shutdown mode. the power switch will be turned off and the sw node will become high impedance. after the part has cooled below 160c, it will r estart. the overtemperature level is not production tested. the ltc7138 additionally implements protection features which inhibit switching when the input voltage is not within a programmable operating range. by use of a resistive divider from the input supply to ground, the run and ovlo pins serve as a precise input supply voltage moni - tor. switching is disabled when either the run pin falls below 1.1v or the ovlo pin rises above 1.21v, which can be configured to limit switching to a specific range of input supply voltage. furthermore, if the input voltage falls below 3.5v typical (3.8v maximum), an internal undervoltage detector disables switching. when switching is disabled, the ltc7138 can safely sustain input voltages up to the absolute maximum rating of 140v. input supply undervoltage or overvoltage events trigger a soft-start reset, which results in a graceful recovery from an input supply transient. (refer to block diagram) ltc7138 7138f
10 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion the basic ltc7138 application circuit is shown on the front page of this data sheet. external component selection is determined by the maximum load current requirement and begins with the selection of the peak current programming resistor, r iset . the inductor value l can then be determined, followed by capacitors c in and c out . maximum output current the maximum average output current is determined by the peak current trip threshold and the valley current trip threshold. with the i set pin open, the peak current com - parator has a minimum threshold of 540ma. the valley current comparator has a minimum threshold of 50% of the peak current, or 270ma. at maximum load, the inductor current ramps between the peak and valley cur - rent thresholds, which results in a maximum load current that is the average of the two, or 405ma. for applications that demand less current, the peak current threshold can be reduced to as low as 140ma, which provides 100ma average output current. this lower peak current allows the efficiency and component selection to be optimized for lower current applications. for applications that require more than 400ma, multiple ltc7138s can be connected in parallel using the fbo pin. see the higher current ap - plications section for more information. the peak current threshold is linearly proportional to the voltage on the i set pin, with 280mv and 1v corresponding to 140ma and 540ma peak current, respectively. the valley current threshold correspondingly changes with the volt - age on the i set pin to remain at 50% of the programmed peak current. this pin may be driven by an external volt - age source to modulate the peak current, which may be beneficial in some applications. usually , the peak current is programmed with an appropriately chosen resistor (r iset ) between the i set pin and ground. the voltage generated on the i set pin by r iset and the internal 5a current source sets the peak current. the value of resistor to achieve a maximum average output current can be computed by using figure 2 or the following equation: r iset = i out(max) ? 1k ? 2ma where 100ma < i out(max) < 405ma. this equation gives the maximum load current supplied using the minimum peak and valley current. for inductor selection, the maxi - mum peak current can then be approximated for a given r iset resistor value as: i peak(max) r iset ? 3.3ma 1k ? + 30ma the peak current is internally limited to be within the range of 140ma to 540ma. shorting the i set pin to ground pro - grams the current limit to 140ma (100ma average output current), and leaving it floating sets the current limit to the maximum value of 540ma (405ma average output current). the internal 5a current source is reduced to 1a in sleep mode to maximize efficiency and to facilitate a trade-off between efficiency and light load output voltage ripple, as described in the optimizing output voltage ripple section. inductor selection for the ltc7138, which has relatively low output current and very high input voltage, switching losses typically dominate the power loss equation. for this architecture, higher inductor values lower the switching frequency which decreases switching loss at the expense of higher dc resistance and lower saturation current. therefore choosing the largest inductor value that satisfies both figure 2. r iset selection r iset (k) 0 current (ma) 200 300 400 500 800 700 600 25 75 100 125 7138 f02 100 0 50 150 175 250 225200 maximum peak inductor current maximum load current ltc7138 7138f
11 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion board area and saturation current requirements yields the highest efficiency in most ltc7138 applications. a good first choice for the inductor can be calculated based on the maximum operating input voltage and the i set pin resistor. if the i set pin is shorted to ground or left open, use 50k or 200k respectively for r iset in the following equation. l = 220h ? v in(max) 150v ? 200k ? r iset an additional constraint on the inductor value is the ltc7138s 150ns minimum switch on-time. therefore, in order to avoid excessive overshoot in the inductor current, the inductor value must be chosen so that it is larger than a minimum value which can be computed as follows: l > v in(max) ? 150ns i peak ? 0.3 ? 1.2 where v in(max) is the maximum input supply voltage when switching is enabled, i peak is the peak current, and the factor of 1.2 accounts for typical inductor tolerance and variation over temperature. with the i set pin open, this minimum inductor value is approximately equal to v in(max) ? 1h/v. although the previous equation provides a minimum in - ductor value, higher efficiency is typically achieved with a larger inductor value, which produces a lower switching frequency . the recommended range of inductor values for small sur face mount inductors as a function of peak current is shown in figure 3. for applications where board area is not a limiting factor, inductors with larger cores can be used, which extends the recommended range of figure 3 to larger values. for applications that have large input supply transients, the ovlo pin can be used to disable switching above the maximum operating voltage v in(max) so that the minimum inductor value is not artificially limited by a transient condition. inductor values that violate the above equation will cause the peak current to overshoot and permanent damage to the part may occur. inductor core selection once the value for l is known, the type of inductor must be selected. high efficiency regulators generally cannot afford the core loss found in low cost powdered iron cores, forcing the use of the more expensive ferrite cores. actual core loss is independent of core size for a fixed inductor value but is very dependent of the inductance selected. as the inductance increases, core losses decrease. un - fortunately, increased inductance requires more turns of wire and therefore copper losses will increase. ferrite designs have ver y low core losses and are pre - ferred at high switching frequencies, so design goals can concentrate on copper loss and preventing satura - tion. ferrite core material saturates hard, which means that inductance collapses abruptly when the peak design current is exceeded. this results in an abrupt increase in inductor ripple current and consequently output voltage ripple. do not allow the core to saturate! different core materials and shapes will change the size/ current and price/current relationship of an inductor. toroid or shielded pot cores in ferrite or permalloy materials are small and do not radiate energy but generally cost more than powdered iron core inductors with similar charac - figure 3. recommended inductor values for maximum efficiency peak inductor current (ma) 100 10 100 inductor value (h) 1000 10000 1000 7138 f03 ltc7138 7138f
12 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion teristics. the choice of which style inductor to use mainly depends on the price versus size requirements and any radiated field/emi requirements. new designs for surface mount inductors are available from coiltronics, coilcraft, tdk, toko, and sumida. catch diode selection the catch diode (d1 from block diagram) conducts current only during the switch off time. average forward current in normal operation can be calculated from: i d(avg) = i out v in C v out v in where i out is the output load current. the maximum av - erage diode current occurs with a shorted output at the high line. for this worst-case condition, the diode current will approach 75% of the programmed peak current. the diode reverse voltage rating should be greater than the maximum operating input voltage. when the ovlo pin is used to limit the maximum operating input voltage, the diode reverse voltage should be greater than the ovlo pin setting, but may be lower than the maximum input voltage during over voltage lockout. for high efficiency at full load, it is important to select a catch diode with a low reverse recovery time and low for - ward voltage drop. as a result, schottky diodes are often used as catch diodes. however, schottky diodes generally exhibit much higher leakage than silicon diodes. in sleep, the catch diode leakage current will appear as load current, and may significantly reduce light load efficiency. diodes with low leakage often have larger forward voltage drops at a given current, so a trade-off can exist between light load and full load efficiency. the selection of schottky diodes with high reverse voltage ratings is limited relative to that of silicon diodes. there - fore, for low reverse leakage and part availability, some applications may prefer a silicon diode. if a silicon diode is necessar y , be sure to select a diode with a specified low reverse recovery time to maximize efficiency. c in and c out selection the input capacitor, c in , is needed to filter the trapezoidal current at the source of the high side mosfet. c in should be sized to provide the energy required to magnetize the inductor without causing a large decrease in input voltage (?v in ). the relationship between c in and ?v in is given by: c in > l ? i peak 2 2 ? v in ? ? v in it is recommended to use a larger value for c in than calculated by the previous equation since capacitance decreases with applied voltage. in general, a 1f x7r ce - ramic capacitor is a good choice for c in in most ltc7138 applications. to prevent large ripple voltage, a low esr input capacitor sized for the maximum rms current should be used. rms current is given by: i rms = i out(max) ? v out v in ? v in v out C 1 this formula has a maximum at v in = 2v out , where i rms = i out /2. this simple worst-case condition is commonly used for design because even significant deviations do not offer much relief. note that ripple current ratings from capacitor manufacturers are often based only on 2000 hours of life which makes it advisable to further derate the capacitor, or choose a capacitor rated at a higher temperature than required. several capacitors may also be paralleled to meet size or height requirements in the design. the output capacitor, c out , filters the inductors ripple current and stores energy to satisfy the load current when the ltc7138 is in sleep. the output ripple has a lower limit of v out /160 due to the 5mv typical hysteresis of the feed - back comparator. the time delay of the comparator adds an additional ripple voltage that is a function of the load current. during this delay time, the l tc7138 continues to switch and supply current to the output. the output ripple ltc7138 7138f
13 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion at light load can be approximated by: ? v out i peak 2 Ci load ? ? ? ? ? ? ? 4 ? 10 C6 c out + v out 160 the output ripple is a maximum at no load and approaches lower limit of v out /160 at full load. choose the output capacitor c out to limit the output voltage ripple ?v out using the following equation: c out i peak ? 2 ? 10 C6 ? v out C v out 160 the value of the output capacitor must also be large enough to accept the energy stored in the inductor without a large change in output voltage during a single switching cycle. setting this voltage step equal to 1% of the output voltage, the output capacitor must be: c out > l 2 ? i peak v out ? ? ? ? ? ? 2 ? 100% 1% typically, a capacitor that satisfies the voltage ripple re - quirement is adequate to filter the inductor ripple. to avoid overheating, the output capacitor must also be sized to handle the ripple current generated by the inductor . the worst-case ripple current in the output capacitor is given by i rms = i peak /2. multiple capacitors placed in parallel may be needed to meet the esr and rms current handling requirements. dry tantalum, special polymer, aluminum electrolytic, and ceramic capacitors are all available in surface mount packages. special polymer capacitors offer very low esr but have lower capacitance density than other types. tantalum capacitors have the highest capacitance density but it is important only to use types that have been surge tested for use in switching power supplies. aluminum electrolytic capacitors have significantly higher esr but can be used in cost-sensitive applications provided that consideration is given to ripple current ratings and long- term reliability. ceramic capacitors have excellent low esr characteristics but can have high voltage coefficient and audible piezoelectric effects. the high quality factor (q) of ceramic capacitors in series with trace inductance can also lead to significant input voltage ringing. input voltage steps if the input voltage falls below the regulated output voltage, the body diode of the internal mosfet will conduct current from the output supply to the input supply. if the input voltage falls rapidly, the voltage across the inductor will be significant and may saturate the inductor. a large current will then flow through the mosfet body diode, resulting in excessive power dissipation that may damage the part. if rapid voltage steps are expected on the input supply, put a small silicon or schottky diode in series with the v in pin to prevent reverse current and inductor saturation, shown below as d1 in figure 4. the diode should be sized for a reverse voltage of greater than the regulated output volt - age, and to withstand repetitive currents higher than the maximum peak current of the l tc7138. figure 4. preventing current flow to the input sw input supply ltc7138 c out 7138 f04 c in v out v in l d1 ceramic capacitors and audible noise higher value, lower cost ceramic capacitors are now be- coming available in smaller case sizes. their high ripple current, high voltage rating, and low esr make them ideal for switching regulator applications. however , care must be taken when these capacitors are used at the input and output. when a ceramic capacitor is used at the input and ltc7138 7138f
14 for more information www.linear.com/ltc7138 v fb v out r2 7138 f06 0.8v r1 v prg1 v prg2 ltc7138 figure 6. setting the output voltage with external resistors a pplica t ions i n f or m a t ion the power is supplied by a wall adapter through long wires, a load step at the output can induce ringing at the input, v in . at best, this ringing can couple to the output and be mistaken as loop instability. at worst, a sudden inrush of current through the long wires can potentially cause a voltage spike at v in large enough to damage the part. for applications with inductive source impedance, such as a long wire, a series rc network may be required in parallel with c in to dampen the ringing of the input supply. figure 5 shows this circuit and the typical values required to dampen the ringing. refer to application note 88 for ad - ditional information on suppressing input supply transients. ceramic capacitors are also piezoelectric. the ltc7138s burst frequency depends on the load current, and in some applications the ltc7138 can excite the ceramic capaci - tor at audio frequencies, generating audible noise. this noise is typically ver y quiet to a casual ear; however , if the noise is unacceptable, use a high performance tantalum or electrolytic capacitor at the output. output voltage programming the ltc7138 has three fixed output voltage modes and an adjustable mode that can be selected with the v prg1 and v prg2 pins. the fixed output modes use an internal feedback divider which enables higher efficiency, higher noise immunity, and lower output voltage ripple for 5v, 3.3v, and 1.8v applications. to select the fixed 5v output voltage, connect v prg1 to ss and v prg2 to gnd. for 3.3v, connect v prg1 to gnd and v prg2 to ss. for 1.8v, connect both v prg1 and v prg2 to ss. for any of the fixed output voltage options, directly connect the v fb pin to v out . for the adjustable output mode (v prg1 = v prg2 = gnd), the output voltage is set by an external resistive divider according to the following equation: v out = 0.8v ? 1 + r1 r2 ? ? ? ? ? ? the resistive divider allows the v fb pin to sense a fraction of the output voltage as shown in figure 6. the output voltage can range from 0.8v to v in . be careful to keep the divider resistors very close to the v fb pin to minimize noise pick-up on the sensitive v fb trace. r = l in c in 4 ? c in c in l in 7138 f05 v in ltc7138 figure 5. series rc to reduce v in ringing to minimize the no-load supply current, resistor values in the megohm range may be used; however, large resistor values should be used with caution. the feedback divider is the only load current when in shutdown. if pcb leakage current to the output node or switch node exceeds the load current, the output voltage will be pulled up. in normal operation, this is generally a minor concern since the load current is much greater than the leakage. to avoid excessively large values of r1 in high output volt - age applications (v out 10v), a combination of external and internal resistors can be used to set the output volt - age. this has an additional benefit of increasing the noise ltc7138 7138f
15 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion the run and ovlo pins can alternatively be configured as precise undervoltage (uvlo) and overvoltage (ovlo) lockouts on the v in supply with a resistive divider from v in to ground. a simple resistive divider can be used as shown in figure 9 to meet specific v in voltage requirements. 4.2m r1 5v r2 7138 f07 v out 800k 0.8v v fb ss v prg1 v prg2 ltc7138 figure 7. setting the output voltage with external and internal resistors run supply ltc7138 run 7138 f08 4.7m 1k v in ltc7138 1k figure 8. run pin interface to logic figure 9. adjustable uv and ov lockout run 7138 f09 r3 v in ltc7138 r4 r5 ovlo immunity on the v fb pin. figure 7 shows the ltc7138 with the v fb pin configured for a 5v fixed output with an external divider to generate a higher output voltage. the internal 5m resistance appears in parallel with r2, and the value of r2 must be adjusted accordingly. r2 should be chosen to be less than 200k to keep the output voltage variation less than 1% due to the tolerance of the ltc7138s internal resistor. the current that flows through the r3-r4-r5 divider will directly add to the shutdown, sleep, and active current of the ltc7138, and care should be taken to minimize the impact of this current on the overall efficiency of the ap - plication circuit. resistor values in the megohm range may be required to keep the impact on quiescent shutdown and sleep currents low . t o pick resistor values, the sum total of r3 + r4 + r5 (r total ) should be chosen first based on the allowable dc current that can be drawn from v in . the individual values of r3, r4 and r5 can then be cal - culated from the following equations: r5 = r total ? 1.21v rising v in ovlo threshold r4 = r total ? 1.21v rising v in uvlo threshold Cr5 r3 = r total Cr5 Cr4 for applications that do not need a precise external ovlo, the ovlo pin should be tied directly to ground. the run pin in this type of application can be used as an external uvlo using the previous equations with r5 = 0. run pin and overvoltage/undervoltage lockout the ltc7138 has a low power shutdown mode controlled by the run pin. pulling the run pin below 0.7v puts the ltc7138 into a low quiescent current shutdown mode (i q ~ 1.4a). when the run pin is greater than 1.21v, switching is enabled. figure 8 shows examples of con - figurations for driving the run pin from logic. ltc7138 7138f
16 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion similarly, for applications that do not require a precise uvlo, the run pin can be tied to v in . in this configuration, the uvlo threshold is limited to the internal v in uvlo thresholds as shown in the electrical characteristics table. the resistor values for the ovlo can be computed using the previous equations with r3 = 0. be aware that the ovlo pin cannot be allowed to exceed its absolute maximum rating of 6v. to keep the voltage on the ovlo pin from exceeding 6v, the following relation should be satisfied: v in(max) ? r5 r3 + r4 + r5 ? ? ? ? ? ? < 6v if this equation cannot be satisfied in the application, connect a 4.7v zener diode between the ovlo pin and ground to clamp the ovlo pin voltage. soft-start soft-start is implemented by ramping the effective refer - ence voltage from 0v to 0.8v. to increase the duration of the soft-start, place a capacitor from the ss pin to ground. an internal 5a pull-up current will charge this capacitor. the value of the soft-start capacitor can be calculated by the following equation: c ss = soft-start time ? 5a 0.8v the minimum soft-start time is limited to the internal soft-start timer of 1ms. when the ltc7138 detects a fault condition (input supply undervoltage/overvoltage or overtemperature) or when the run pin falls below 1.1v, the ss pin is quickly pulled to ground and the internal soft-start timer is reset. this ensures an orderly restart when using an external soft-start capacitor. note that the soft-start capacitor may not be the limiting factor in the output voltage ramp. the maximum output current, which is equal to half of the peak current, must charge the output capacitor from 0v to its regulated value. for small peak currents or large output capacitors, this ramp time can be significant. therefore, the output voltage ramp time from 0v to the regulated v out value is limited to a minimum of ramp time 1.33 ? c out i peak v out optimizing output voltage ripple after the peak current resistor and inductor have been selected to meet the load current and frequency require - ments, an optional capacitor, c iset can be added in parallel with r iset to reduce the output voltage ripple dependency on load current. at light loads the output voltage ripple will be a maximum. the peak inductor current is controlled by the voltage on the i set pin. the current out of the i set pin is 5a while the ltc7138 is active and is reduced to 1a during sleep mode. the i set current will return to 5a on the first switching cycle after sleep mode. placing a parallel rc network to ground on the i set pin filters the i set voltage as the ltc7138 enters and exits sleep mode, which in turn will affect the output voltage ripple, efficiency, and load step transient performance. higher current applications for applications that require more than 400ma, the ltc7138 provides a feedback comparator output pin (fbo) for driving additional ltc7138s. when the fbo pin of a master ltc7138 is connected to the v fb pin of one or more slave ltc7138s, the master controls the burst cycle of the slaves. figure 10 shows an example of a 5v, 800ma regulator using two ltc7138s. the master is configured for a 5v fixed output with external soft-start and v in uvlo/ovlo levels set by the run and ovlo pins. since the slave is directly controlled by the master, its ss pin should be float - ing, run should be tied to v in , and ovlo should be tied to ground. furthermore, the slave should be configured for a 1.8v fixed output (v prg1 = v prg2 = ss) to set the ltc7138 7138f
17 for more information www.linear.com/ltc7138 v fb sw l1 l2 v in run r3 c in c out v out 5v 800ma c ss v in r4 r5 ovlo ss v prg1 v prg2 fbo ltc7138 (master) sw anode v fb v in run ovlo ss v prg1 v prg2 fbo 7138 f10 ltc7138 (slave) anode d2 d1 figure 10. 5v, 800ma regulator a pplica t ions i n f or m a t ion the junction temperature is given by: t j = t a + t r generally, the worst-case power dissipation is in dropout at low input voltage. in dropout, the ltc7138 can provide a dc current as high as the full 575ma peak current to the output. at low input voltage, this current flows through a higher resistance mosfet, which dissipates more power. as an example, consider the ltc7138 in dropout at an input voltage of 5v, a load current of 610ma and an ambient temperature of 85c. from the typical performance graphs of switch on-resistance, the r ds(on) of the top switch at v in = 5v and 100c is approximately 3.2. therefore, the power dissipated by the part is: p d = (i load ) 2 ? r ds(on) = (610ma) 2 ? 3.2 = 1.19w for the msop package the ja is 40c/w. thus, the junc - tion temperature of the regulator is: t j = 85 c + 1.19w ? 40 c w = 133 c which is below the maximum junction temperature of 150c. note that the while the ltc7138 is in dropout, it can provide output current that is equal to the peak current of the part. this can increase the chip power dissipation dramatically and may cause the internal overtemperature protection circuitry to trigger at 180c and shut down the ltc7138. pin clearance/creepage considerations the ltc7138 mse package has been uniquely designed to meet high voltage clearance and creepage requirements. pins 2, 4, 13, and 15 are omitted to increase the spac - ing between adjacent high voltage solder pads (v in , sw, and run) to a minimum of 0.657mm which is sufficient for most applications. for more information, refer to the printed circuit board design standards described in ipc- 2221 (www.ipc.org). v fb pin threshold at 1.8v. the inductors l1 and l2 do not necessarily have to be the same, but should both meet the criteria described in the inductor selection section. thermal considerations in most applications, the ltc7138 does not dissipate much heat due to its high efficiency. but, in applications where the ltc7138 is running at high ambient temperature with low supply voltage and high duty cycles, such as dropout, the heat dissipated may exceed the maximum junction temperature of the part. to prevent the ltc7138 from exceeding the maximum junction temperature, the user will need to do some thermal analysis. the goal of the thermal analysis is to determine whether the power dissipated exceeds the maximum junc - tion temperature of the part. the temperature rise from ambient to junction is given by: t r = p d ? ja where p d is the power dissipated by the regulator and ja is the thermal resistance from the junction of the die to the ambient temperature. ltc7138 7138f
18 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion design example as a design example, consider using the ltc7138 in an application with the following specifications: v in = 36v to 72v (48v nominal), v out = 12v, i out = 400ma, and that switching is enabled when v in is between 30v and 90v. first, calculate the inductor value: l = 220h ? 90v 150v = 132h choose a 150h inductor as a standard value. next, verify that this meets the l min requirement at the maximum input voltage: l min = 90v ? 150ns 0.610a ? 0.3 ? 1.2 = 89h therefore, the minimum inductor requirement is satisfied and the 150h inductor value may be used. next, c in and c out are selected. for this design, c in should be sized for a current rating of at least: i rms = 400ma ? 12v 36v ? 36v 12v C 1 ? 189ma rms the value of c in is selected to keep the input from droop - ing less than 1v at low line: c in > 150h ? 0.61a 2 2 ? 36v ? 1v ? 0.76f since the capacitance of capacitors decreases with dc bias, a 1f capacitor should be chosen. the catch diode should have a reverse voltage rating of greater than the overvoltage lockout setting of 90v. it should also be rated for an average forward current of at least: i d(avg) = 400ma 90v C 12v 90v = 347ma for margin, select a catch diode with a reverse breakdown of at least 100v and an average current of 400ma or higher. c out will be selected based on a value large enough to satisfy the output voltage ripple requirement. for a 1% output ripple (120mv), the value of the output capacitor can be calculated from: c out 0.61a ? 2 ? 10 C6 120mv C 12v 160 ? 27f c out also needs an esr that will satisfy the output voltage ripple requirement. the required esr can be calculated from: esr < 120mv 0.61a ? 197m ? a 33f ceramic capacitor has significantly less esr than 197m. the output voltage can now be programmed by choosing the values of r1 and r2. since the output volt - age is higher than 10v, the ltc7138 should be set for a 5v fixed output with an external divider to divide the 12v output down to 5v. r2 is chosen to be less than 200k to keep the output voltage variation to less than 1% due to the internal 5m resistor tolerance. set r2 = 196k and calculate r1 as: ? r1 = 12v C 5v 5v ? 196k ? ? 5m ? ( ) = 264k ? choose a standard value of 267k for r1. ltc7138 7138f
19 for more information www.linear.com/ltc7138 a pplica t ions i n f or m a t ion the undervoltage and overvoltage lockout requirements on v in can be satisfied with a resistive divider from v in to the run and ovlo pins (refer to figure 9). choose r3 + r4 + r5 = 2.5m to minimize the loading on v in . calculate r3, r4 and r5 as follows: r5 = 1.21v ? 2.5m ? v in _ ov(rising) = 33.6k r4 = 1.21v ? 2.5m ? v in _ uv(rising) Cr5 = 67.2k r3 = 2.5m ? Cr4 Cr5 = 2.4m since specific resistor values in the megohm range are generally less available, it may be necessary to scale r3, r4, and r5 to a standard value of r3. for this example, choose r3 = 2.2m and scale r4 and r5 by 2.2m/2.4m. then, r4 = 61.6k and r5 = 30.8k. choose standard values of r3 = 2.2m, r4 = 62k, and r5 = 30.9k. note that the fall - ing thresholds for both uvlo and ovlo will be 10% less than the rising thresholds, or 27v and 81v respectively. the i set pin should be left open in this example to select maximum peak current (610ma). figure 11 shows a complete schematic for this design example. pc board layout checklist when laying out the printed circuit board, the following checklist should be used to ensure proper operation of the ltc7138. check the following in your layout: 1. large switched currents flow in the power switch, catch diode, and input capacitor. the loop formed by these components should be as small as possible. a ground plane is recommended to minimize ground impedance. 2. connect the (+) terminal of the input capacitor, c in , as close as possible to the v in pin. this capacitor provides the ac current into the internal power mosfet. 3. keep the switching node, sw, away from all sensitive small signal nodes. the rapid transitions on the switching node can couple to high impedance nodes, in particular v fb , and create increased output ripple. 7138 f11 v fb i set fbo sw anode 150h v in run 2.2m 267k 196k 1f 33f v out 12v 400ma v in 36v to 72v 62k 30.9k ovlo v prg2 ltc7138 ss v prg1 gnd figure 11. 36v to 72v input to 12v output, 400ma regulator v fb anode i set sw l1 v in run r3 r1 d1 r2 c in c out v out v in r4 r iset r5 ovlo v prg1 ss v prg2 ltc7138 gnd fbo c ss 7138 f12 c out v out v in gnd gnd r3 r iset c ss r5 vias to ground plane vias to input supply (v in ) vias to output supply (v out ) outline of local ground plane r4 r1 r2 l1 c in d1 figure 12. example pcb layout ltc7138 7138f
20 for more information www.linear.com/ltc7138 v in input voltage (v) 0 efficiency (%) 85 90 100 95 150 120 7138 f13b 80 75 50 60 30 60 90 70 65 55 i out = 100ma v out = 5v v out = 3.3v v out = 1.8v v in input voltage (v) 0 maximum load current (ma) 400 250 200 350 300 150 100 150 120 7138 ta04b 50 30 60 90 v out = ?5v v out = ?15v output voltage 500mv/div 10ms/div 7138 f14b 10 load l1: coilcraft mss1278t-334kl d1: diodes inc pds3200 *v out = v in for v in < 5v 7138 f13 v fb i set sw anode l1 330h v in run c in 1f 250v x7r c out 47f 6.3v x5r v out * 5v 400ma v in 4v to 140v ss ovlo v prg1 v prg2 ltc7138 gnd fbo d1 efficiency vs input voltage typical a pplica t ions 4v to 125v input to C15v output positive-to-negative regulator 7138 f14 v fb ss sw l1 150h v in run c in 1f 250v x7r c out 100f 2 6.3v x5r v out 3.3v 400ma v in 4v to 140v i set v prg2 v prg1 ovlo ltc7138 gnd fbo 470nf 220pf* l1: sumida cdrh104rnp-151nc d1: vishay u1d *optional components for lower light-load output volage ripple 220k* anode d1 7138 ta04a v fb i set sw anode l1 220h v in run c in 1f 250v x7r c out 22f 25v x5r v out ?15v v in 4v to 125v ss ovlo v prg1 v prg2 ltc7138 gnd fbo 200k 102k maximum load current v in v in + v out ? 3 ? i peak 4 maximum input voltage = 140 ?|v out | l1: tdk slf12555-221mr72 d1: st micro stth102a d1 soft-start waveform maximum load current vs input voltage figure 13. high efficiency 400ma regulator figure 14. 3.3v/400ma regulator with 75ms soft-start ltc7138 7138f
21 for more information www.linear.com/ltc7138 l1 current 500ma/div v in /v out 5v/div l2 current 500ma/div 1s/div 7138 ta05b v in v out l1 current 500ma/div v in 50v/div v out 10v/div l2 current 500ma/div 200ms/div 7138 ta05c transient to 140v 72v v in input voltage (v) 30 efficiency (%) 85 90 100 95 150 120 7138 ta03b 80 60 90 pwm open v dim open 10w led driver 7138 ta03a v fb ovlo sw l1 100h v in c in 1f 250v x7r c out 4.7f 50v x7r v out m1 25v led 400ma v in 32v to 140v fbo v prg2 i set v dim v prg1 ss run ltc7138 gnd 1m 42.2k 1m 27.4k 3.3v pwm l1: tdk slf10145t-101m d1: toshiba crh01 m1: vishay siliconix si2356ds v dim = 0.1v to 1v for 10:1 analog dimming pwm = square wave for digital dimming 30v overvoltage protection on v out d1 anode low dropout startup and shutdown overvoltage lockout operation efficiency vs input voltage typical a pplica t ions 7138 ta05a v fb i set sw l1 100h v in run c in1 1f 250v x7r c in2 1f 250v x7r c out 47f 16v x5r v out * 12v 800ma v in 4v to 90v up to 140v transient ss fbo v prg1 v prg2 ovlo ltc7138 (master) gnd v fb i set sw l2 100h v in run fbo ss v prg2 v prg1 ovlo anode ltc7138 (slave) gnd 1m 13.7k 267k 196k l1/l2: wrth 744 770 910 1 d1/d2: central semi cmsh1-100m-ltn *v out = v in for v in < 12v d2 d1 anode 4v to 90v input to 12v/800ma output regulator with overvoltage lockout ltc7138 7138f
22 for more information www.linear.com/ltc7138 typical a pplica t ions 36v to 140v to 36v/400ma with 120ma input current limit 5v to 140v input to 5v/400ma output with 20khz minimum switching frequency l1: tdk slf12555t-101m1r1 d1: rohm rf101l2s 7138 ta06a v fb ss sw l1 100h v in run c in 1f 250v x7r c out 4.7f 50v x7r v out 36v 400ma* v in 36v to 140v i set ovlo ltc7138 gnd fbo 220k 35.7k r2 4.02k r1 470k v prg1 v prg2 i nput current limit = v out 2.5 ? r2 r1 + r2 ? 1 + 5a ? r1 v in ? ? ? ? ? ? v out 2.5 ? r2 r1 + r2 * maximum load current = v in 36v ? 120ma 400ma d1 anode maximum load and input current vs input voltage input current vs load current switching frequency vs load current 7138 ta08a v fb sw anode l1 150h v in run c in 1f 250v c out 22f v out 5v 400ma v in 5v to 140v v prg1 v prg2 ovlo ltc7138 gnd i set fbo ss 953k 6.8 2n7000 100k 175k out set v + in div ltc6994-1 gnd l1: coiltronics dr74-101-r d1: diodes inc murs120-13-f d1 v in input voltage (v) 40 maximum current (ma) 400 500 150 140130120110 7138 ta06b 0 50 807060 10090 200 300 100 maximum load current maximum input current 0.1 100 1000 10 1 load current (ma) switching frequency (khz) 100 1 10 7138 ta08b 0.01 0.1 without frequency limit with frequency limit v in = 48v 0.1 100 1000 10 1 load current (ma) input current (ma) 100 1 10 7138 ta08c 0.01 0.1 without frequency limit with frequency limit v in = 48v ltc7138 7138f
23 for more information www.linear.com/ltc7138 information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no representa - tion that the interconnection of its circuits as described herein will not infringe on existing patent rights. msop (mse16(12)) 0213 rev d 0.53 0.152 (.021 .006) seating plane 0.18 (.007) 1.10 (.043) max 0.17 ?0.27 (.007 ? .011) typ 0.86 (.034) ref 0.50 (.0197) bsc 1.0 (.039) bsc 1.0 (.039) bsc 16 16 14 121110 1 3 5 6 7 8 9 9 1 8 note: 1. dimensions in millimeter/(inch) 2. drawing not to scale 3. dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.152mm (.006") per side 4. dimension does not include interlead flash or protrusions. interlead flash or protrusions shall not exceed 0.152mm (.006") per side 5. lead coplanarity (bottom of leads after forming) shall be 0.102mm (.004") max 6. exposed pad dimension does include mold flash. mold flash on e-pad shall not exceed 0.254mm (.010") per side. 0.254 (.010) 0 ? 6 typ detail ?a? detail ?a? gauge plane 5.10 (.201) min 3.20 ? 3.45 (.126 ? .136) 0.889 0.127 (.035 .005) recommended solder pad layout 0.305 0.038 (.0120 .0015) typ 0.50 (.0197) bsc bottom view of exposed pad option 2.845 0.102 (.112 .004) 2.845 0.102 (.112 .004) 4.039 0.102 (.159 .004) (note 3) 1.651 0.102 (.065 .004) 1.651 0.102 (.065 .004) 0.1016 0.0508 (.004 .002) 3.00 0.102 (.118 .004) (note 4) 0.280 0.076 (.011 .003) ref 4.90 0.152 (.193 .006) detail ?b? detail ?b? corner tail is part of the leadframe feature. for reference only no measurement purpose 0.12 ref 0.35 ref mse package variation: mse16 (12) 16-lead plastic msop with 4 pins removed exposed die pad (reference ltc dwg # 05-08-1871 rev d) p ackage descrip t ion please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. ltc7138 7138f
24 for more information www.linear.com/ltc7138 ? linear technology corporation 2015 lt 0115 ? printed in usa linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax : (408) 434-0507 www.linear.com/ltc7138 r ela t e d p ar t s typical a pplica t ion 12v/400ma automotive supply *v out ? v in for v in < 12v v out 12v* 400ma 7138 ta07 v fb i set sw anode l1 220h v in run c in 1f 250v x7r c out 22f 16v x7r v in 4v to 140v ss ovlo v prg1 v prg2 ltc7138 gnd fbo 267k 196k l1: coilcraft mss1246t-224kl d1: diodes inc sbr1u200p1-7 d1 part number description comments ltc3638 140v, 250ma micropower step-down dc/dc regulator v in : 4v to 140v, v out(min) = 0.8v, i q = 12a, i sd = 1.4a, ms16e package l tc3639 150v , 100ma synchronous micropower step-down dc/dc regulator v in : 4v to 150v, v out(min) = 0.8v, i q = 12a, i sd = 1.4a, ms16e package l tc3637 76v , 1a high efficiency step-down dc/dc regulator v in : 4v to 76v, v out(min) = 0.8v, i q = 12a, i sd = 3a, 3mm 5mm dfn16, msop16e packages l tc3630a 76v , 500ma synchronous step-down dc/dc regulator v in : 4v to 76v, v out(min) = 0.8v, i q = 12a, i sd = 5a, 3mm 5mm dfn16, msop16e packages l tc3810 100v synchronous step-down dc/dc controller v in : 6.4v to 100v, v out(min) = 0.8v, i q = 2ma, i sd < 240a, ssop28 package l tc3631/l tc3631-3.3 ltc3631-5 45v (transient to 60v), 100ma synchronous step-down dc/dc regulator v in : 4.5v to 45v, v out(min) = 0.8v, i q = 12a, i sd < 3a, 3mm 3mm dfn8, msop8 packages l tc3642 45v (t ransient to 60v), 50ma synchronous step-down dc/dc regulator v in : 4.5v to 45v, v out(min) = 0.8v, i q = 12a, i sd < 3a, 3mm 3mm dfn8, msop8 packages l tc3632 50v (t ransient to 60v), 20ma synchronous step-down dc/dc regulator v in : 4.5v to 45v, v out(min) = 0.8v, i q = 12a, i sd < 3a, 3mm 3mm dfn8, msop8 packages l tc3891 60v synchronous step-down dc/dc controller with burst mode operation v in : 4v to 60v, v out(min) = 0.8v, i q = 50a, i sd < 14a, 3mm 4mm qfn20, tssop20e packages l tc4366-1/l tc4366-2 high voltage surge stopper v in : 9v to >500v, adjustable output clamp voltage, i sd < 14a, 2mm 3mm dfn8, tsot-8 packages efficiency and power loss vs load current v in = 24v v in = 48v v in = 120v load current (ma) 30 efficiency (%) power loss (mw) 90 100 20 10 80 50 70 10 1 100 60 40 7138 ta07b 0 efficiency power loss 1000 0.1 100 1000 10 1 ltc7138 7138f

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